ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter Bruce Jacob University of Maryland ECE Dept. SLIDE 1
ENEE 359a Digital VLSI Circuits P/N Junction, MOS Transistors, CMOS Inverter Prof. Bruce Jacob
[email protected]
Credit where credit is due: Slides contain original artwork (© Jacob 2004) as well as material taken liberally from Irwin & Vijay’s CSE477 slides (PSU), Schmit & Strojwas’s 18-322 slides (CMU), Wolf’s slides for Modern VLSI Design, and/or Rabaey’s slides (UCB). Device physics: http://hyperphysics.phy-astr.gsu.edu/hbase/solids/sselcn.html UNIVERSITY OF MARYLAND
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
Overview
Bruce Jacob University of Maryland ECE Dept. SLIDE 2
UNIVERSITY OF MARYLAND
•
Electrons & holes, bands & band gaps, insulators, conductors, semiconductors
•
Silicon crystal lattice & doping
•
P/N junction & parasitic capacitance
•
n-type/n-channel MOSFET
•
Timing analysis of MOSFET, capacitance
•
Body effect, series-connected FETs
•
CMOS inverter: timing, switching threshold, transistor sizing
•
Dynamic behavior (preview)
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
What Is Conductivity?
Bruce Jacob University of Maryland ECE Dept.
Perspective from Band Theory of Solids:
Energy of electrons
Large band gap (not “Gap Band”) between valence and conduction bands in insulator material suggests that, at ordinary temperatures, no electrons can reach conduction band (i.e. material won’t conduct)
Conduction Band
In semiconductors, the band gap is small enough that thermal energy can bridge gap for small fraction of electrons.
SLIDE 3
In conductors, there is no band gap (conduction and valence bands overlap).
INSULATOR
SEMICONDUCTOR
Fermi level
CONDUCTOR Fermi level
Conduction Band Valence Band UNIVERSITY OF MARYLAND
Valence Band
Conduction Band Valence Band
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
Silicon, Specifically
Bruce Jacob University of Maryland ECE Dept. SLIDE 4
Si
14 protons in nucleus 4 valence electrons
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ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
Silicon, Specifically
Bruce Jacob University of Maryland ECE Dept.
Si
SLIDE 5
Si
Shared electrons of covalent bonds
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Si
Si
Si
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
Silicon, Specifically
Bruce Jacob University of Maryland ECE Dept.
Silicon Lattice (artistic license exploited) Si
Si
Si
Si
Si
Si
Si
Si
Si
Si
Si
Si
Si
Si
Si
Si
Si
Si
Si
Si
SLIDE 6
UNIVERSITY OF MARYLAND
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
Silicon, Specifically
Bruce Jacob University of Maryland ECE Dept.
Silicon Lattice — It is a semiconductor Si
Si
Si
Si
Si
Si
Si
Si
Si
Si
Si
Si
Si
Si
Si
Free Si electron
Si
SLIDE 7
Hole Si UNIVERSITY OF MARYLAND
Si
Si
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
Silicon, Specifically
Bruce Jacob University of Maryland ECE Dept.
Semiconductor current: electron/hole flow
SLIDE 8
UNIVERSITY OF MARYLAND
Si
Si
Si
Si
Si
Si
Si
Si
Si
Si
Si
Si
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
Silicon, Specifically
Bruce Jacob University of Maryland ECE Dept.
Perspective from Band Theory of Solids: Energy of electrons
SLIDE 9
0K (no electrons in conduction band)
Conduction Band Fermi level
Valence Band
• UNIVERSITY OF MARYLAND
300K
Free electrons
Conduction Band
1.09 eV
Holes
Valence Band
Conductivity is non-zero; mobile electrons/holes in conduction/valence band; can be increased w/ doping
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
Silicon, Specifically
Bruce Jacob University of Maryland ECE Dept.
Doping: small % of foreign atoms in lattice
SLIDE 10
P
B
Breaks up regular lattice, produces dramatic changes in electrical properties •
•
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Donors: pentavalent impurities (5 valence electrons) produce n-type semiconductors by adding electrons. E.g. antimony, arsenic, phosphorus Acceptors: trivalent impurities (3 valence electrons) produce p-type semiconductors by adding electron deficiencies (“holes”). E.g. boron, aluminum, gallium
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
P-Type Semiconductor
Bruce Jacob University of Maryland ECE Dept.
Si
Acceptor impurity creates a hole
SLIDE 11
Si
B
Si
Si
Conduction Band Extra hole energy levels
Valence Band Addition of acceptor impurities contributes hole energy levels low in the semiconductor band gap so that electrons can be easily excited from the valence band into these levels, leaving mobile holes in the valence band. This shifts the effective Fermi level to a point about halfway between the acceptor levels and the valence band. Electrons can be elevated from the valence band to the holes in the band gap with the energy provided by an applied voltage. Since electrons can be exchanged between the holes, the holes are said to be mobile. Holes are said to be the “majority carriers” for current flow in a p-type semiconductor. UNIVERSITY OF MARYLAND
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
N-Type Semiconductor
Bruce Jacob University of Maryland ECE Dept.
Si Donor impurity creates free electron
SLIDE 12
Si
P
Si
Si
Conduction Band Extra electron energy levels
Valence Band Addition of donor impurities contributes electron energy levels high in the semiconductor band gap so that electrons can be easily excited into the conduction band. This shifts the Fermi level to a point about halfway between the donor levels and the conduction band. Electrons can be elevated to the conduction band with the energy provided by an applied voltage and move through the material. Electrons are said to be the “majority carriers” for current flow in an n-type semiconductor. UNIVERSITY OF MARYLAND
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
One Way to Think About It
Bruce Jacob University of Maryland ECE Dept.
Acceptor side
Donor side
Conduction Band
Conduction Band
SLIDE 13
Extra hole energy levels Extra electron energy levels
Valence Band
P-type •
•
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Valence Band
N-type
P-type: Conduction band is pulled down close to the valence band by the creation of available holes (willing acceptors of free electrons) N-type: Valence band is pushed up close to the conduction band by the addition of mobile electrons
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
The P/N Junction
Bruce Jacob University of Maryland ECE Dept.
Acceptor side
Donor side
Conduction Band
Conduction Band
SLIDE 14
Extra hole energy levels Extra electron energy levels
Valence Band
P-type •
•
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Valence Band
N-type
P-type: extra holes in band gap allow excitation of valence-band electrons, leaving mobile holes in valence band N-type: electron energy levels near the top of the band gap allow easy excitation of electrons into conduction band
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter Bruce Jacob University of Maryland ECE Dept.
The P/N Junction Acceptor side Donor side
Conduction Band
SLIDE 15
Extra hole energy levels
Conduction Band Extra electron energy levels
Valence Band
Valence Band
Diode P-type silicon
N-type silicon
p-n junction
UNIVERSITY OF MARYLAND
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
The P/N Junction
Bruce Jacob University of Maryland ECE Dept.
DEPLETION REGION
SLIDE 16
If not touching, nothing happens
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ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
The P/N Junction
Bruce Jacob University of Maryland ECE Dept.
DEPLETION REGION
SLIDE 17
With a connection, electrons from n-region in conduction band diffuse across junction and combine with holes in p-region (why doesn’t this continue indefinitely?) UNIVERSITY OF MARYLAND
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
The P/N Junction
Bruce Jacob University of Maryland ECE Dept.
DEPLETION REGION Negative ion
Positive ion
SLIDE 18
Mobile hole
depletion region
Mobile electron
Ions are formed on both sides of junction (negative ion from filled hole; positive ion from removed electron). This forms a space charge that impedes further electron flow. UNIVERSITY OF MARYLAND
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
The P/N Junction
Bruce Jacob University of Maryland ECE Dept.
DEPLETION REGION
SLIDE 19
Cj
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two plates of a capacitor
Parasitic capacitance:
Built-in junction potential:
C j0 C j = -----------------------m Vd 1 – -----φ0
N A N D φ 0 = φ T ⋅ ln --------------- n2 i
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
The P/N Junction
Bruce Jacob University of Maryland ECE Dept.
BIAS EFFECT on DEPLETION REGION Equilibrium
SLIDE 20
P
N depletion region
Conduction Band Extra hole energy levels
Valence Band
Conduction Band Extra electron energy levels
Valence Band • • UNIVERSITY OF MARYLAND
Upward = increased electron energy (must supply energy to make electron go up or hole to go down) Drift-diffusion equilibrium (current is flowing)
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
The P/N Junction
Bruce Jacob University of Maryland ECE Dept. SLIDE 21
BIAS EFFECT on DEPLETION REGION Forward Bias P
N depletion region still exists
Conduction Band
Conduction Band
Extra hole energy levels Extra electron energy levels
Valence Band Valence Band P-side is made more positive relative to N-side, making it “downhill” to move an electron across the junction. Electron on N-side can fill a vacancy (“hole”) on P-side & move from hole to hole to the left to positive terminal (hole “moves” right).
UNIVERSITY OF MARYLAND
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
The P/N Junction
Bruce Jacob University of Maryland ECE Dept. SLIDE 22
BIAS EFFECT on DEPLETION REGION Reverse Bias P
N depletion region increases in size until new potential = applied bias
Conduction Band Extra hole energy levels
Valence Band Conduction Band P-side is made more negative relative to N-side, making it “uphill” to move an electron across the junction. Applied voltage impedes the flow of N-region electrons across the p/n junction. Initial transient electron flow is left to right; it stops when potential (widening depletion region) equals the applied voltage. UNIVERSITY OF MARYLAND
Extra electron energy levels
Valence Band
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter Bruce Jacob
MOS Transistors MOS Transistor, reverse-biased:
University of Maryland ECE Dept. SLIDE 23
N-Doped Region [mobile electrons]
PN Junction
n
P-Doped Region [mobile holes]
p-doped semiconductor substrate UNIVERSITY OF MARYLAND
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter Bruce Jacob
MOS Transistors MOS Transistor, reverse-biased:
University of Maryland ECE Dept. SLIDE 24
VDD
VDD P-Doped Region [acceptor holes]
n
N-Doped Regions [donor electrons]
n
p-doped semiconductor substrate UNIVERSITY OF MARYLAND
VSS
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter Bruce Jacob
MOS Transistors MOS Transistor, reverse-biased:
University of Maryland ECE Dept. SLIDE 25
VDD
VDD Insulator (gate oxide)
n
n
p-doped semiconductor substrate UNIVERSITY OF MARYLAND
VSS
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter Bruce Jacob
MOS Transistors NMOS Transistor with gate:
University of Maryland ECE Dept.
0
SLIDE 26
+
+ Conductor
Insulator (gate oxide)
n
n
p-doped semiconductor substrate UNIVERSITY OF MARYLAND
0
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter Bruce Jacob
MOS Transistors NMOS Transistor with bias voltages:
University of Maryland ECE Dept.
0
SLIDE 27
0
+ Conductor
Insulator (gate oxide)
n
n
p-doped semiconductor substrate UNIVERSITY OF MARYLAND
0
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter Bruce Jacob
MOS Transistors NMOS Transistor with bias voltages:
University of Maryland ECE Dept.
+
SLIDE 28
0
+ Gate (conductor)
Insulator (gate oxide)
n
n CURRENT
p-doped semiconductor substrate UNIVERSITY OF MARYLAND
0
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter Bruce Jacob
MOS Transistors NMOS Transistor, two views:
University of Maryland ECE Dept.
Length
SLIDE 29
Width
TOP VIEW Gate
FOX n SIDE VIEW UNIVERSITY OF MARYLAND
Gate oxide n
p-doped semiconductor substrate
FOX
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter Bruce Jacob
MOS Transistors NMOS Transistor with bias voltages:
University of Maryland ECE Dept.
Gate Source
Drain
SLIDE 30
n
channel
VSS
n
p-doped semiconductor substrate
Gate Source
0
Gate Drain
0
V>0
Source
0
Drain
V>0
Electron Flow UNIVERSITY OF MARYLAND
V>0
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter Bruce Jacob
MOS Transistors PMOS Transistor with bias voltages:
University of Maryland ECE Dept.
Gate Drain
Source
SLIDE 31
p
channel
VDD
p
n-doped semiconductor substrate
Gate Drain
0
Gate Source
VDD
V>0
Drain
0
Source
V0
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter Bruce Jacob University of Maryland ECE Dept.
MOS Transistors MOS Transistors: Gate
Gate Source
Source
Drain
Drain
SLIDE 32
n
channel
VSS
n
p-doped semiconductor substrate
p
PMOS
Gate
UNIVERSITY OF MARYLAND
Gate
Drain
Substrate
VDD
p
n-doped semiconductor substrate
NMOS Source
channel
Source
Drain
Substrate
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
0.25 µm transistor (Bell Labs)
Bruce Jacob University of Maryland ECE Dept.
Silicide
SLIDE 33
Poly Gate oxide
Source & Drain
Poly+silicide = “polycide gate” (lower R) UNIVERSITY OF MARYLAND
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter Bruce Jacob
MOS Behavior VSource
University of Maryland ECE Dept.
VDrain
Gate n+
n+
SLIDE 34
p (bulk)
UNIVERSITY OF MARYLAND
VGate
Depletion Regions
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
MOS Behavior VGate
VSource
Bruce Jacob University of Maryland ECE Dept.
VDrain
Gate n+
n+
SLIDE 35
p (bulk)
VS = 0V
Depletion Regions
VG = 0.5V
VD = 0V
Charge Density Gate Oxide Substrate (p-type)
Depletion layer
x (depth) UNIVERSITY OF MARYLAND
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
MOS Behavior VSource
Bruce Jacob
Channel
University of Maryland ECE Dept.
VGate VDrain Free electrons
Gate n+
SLIDE 36
n+
Depletion Regions
p (bulk)
VS = 0V
Inversion Layer forms when
VGS > VT
Assume VT = 0.75V (threshold voltage)
VD = 0V
VG = 1V
Charge Density Gate Oxide Substrate (p-type)
Inversion layer
Depletion layer
x (depth) UNIVERSITY OF MARYLAND
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
MOS Behavior: linear region VGate
VSource
Bruce Jacob University of Maryland ECE Dept.
VDrain
Gate n+
SLIDE 37
n+
Inversion Layer existence requires VGS – VT > V(y)
p (bulk)
VD = 0.001V
VG = 1V
VS = 0V
Assume VT = 0.75V (threshold voltage)
ε ox W = µ n ------- ----- ( V GS – V T )V DS t ox L dielectric constant
electron mobility
I DS
oxide thickness
VGS – V(y)
V(y) 1V
VDS
0.75V
y (channel)
y (channel)
True when VGS > VT & VDS V(y)
p (bulk)
Assume VT = 0.75V (threshold voltage)
VD = 0.15V VG = 1V VS = 0V dielectric constant electron mobility ε ox W 1 2 I DS = µ n ------- ----- ( V GS – V T )V DS – --- V DS t ox L 2 oxide thickness
VGS – V(y)
V(y) VDS
1V 0.85V 0.75V
y (channel)
y (channel)
True when VGS > VT & VDS ≤ VGS – VT UNIVERSITY OF MARYLAND
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
MOS Behavior: saturation VGate
VSource
Bruce Jacob University of Maryland ECE Dept.
VDrain
Gate n+
n+
SLIDE 39
Inversion Layer “pinched off” when
VDS = VGS – VT
p (bulk)
VS = 0V I DS
Assume VT = 0.75V (threshold voltage)
VD = 0.25V
VG = 1V
1 ε ox W 2 = --- µ n ------- ----- ( V GS – V T ) 2 t ox L VGS – V(y)
V(y) VDS
1V 0.75V
y (channel)
y (channel)
True when VGS > VT & VDS = VGS – VT UNIVERSITY OF MARYLAND
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
MOS Behavior: modulation VGate
VSource
Bruce Jacob University of Maryland ECE Dept.
VDrain
Gate n+
n+
SLIDE 40
Inversion Layer does not exist here
VDS ≥ VGS – VT
p (bulk)
VS = 0V I DS V(y)
Assume VT = 0.75V (threshold voltage)
VD = 0.35V
VG = 1V
1 ε ox W 2 ---------= µ ( V – V T ) ( 1 + λ V DS ) 2 n t ox L GS effective channel length decreases
VDS
1V
y (channel)
0.75V 0.65V
VGS – V(y)
length modulation factor
over this range, effective gate potential is not sufficient to create inversion layer
y (channel)
True when VGS > VT & VDS ≥ VGS – VT UNIVERSITY OF MARYLAND
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
Example of Drain Current
Bruce Jacob University of Maryland ECE Dept.
Values for generic 0.5 µm process: ε ox k’ (transconductance) = µ n ------t ox
VT
n-type
k’n = 73 µA/V2
0.7V
p-type
k’p = 21 µA/V2
-0.8V
SLIDE 41
Assume W/L = 3/2, VGS = 2V, find IDS for NMOS device at saturation point: 1 W 2 I DS = --- k' ----- ( V GS – V T ) 2 L 1 µA 3 2 I DS = --- 73 -------2 --- ( 2V – 0.7V ) = 93µA 2 V 2 UNIVERSITY OF MARYLAND
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
NMOS I-V Plot
Bruce Jacob University of Maryland ECE Dept.
2.5
X 10-4
VGS = 2.5V
ID (A)
VGS = 2.0V
1.5 1
VGS = 1.5V
0.5
VGS = 1.0V
Linear dependence
2
SLIDE 42
0 0
0.5
1
1.5
2
2.5
VDS (V) NMOS transistor, 0.25um, Ld = 0.25um, W/L = 1.5, VDD = 2.5V, VT = 0.4V
UNIVERSITY OF MARYLAND
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter Bruce Jacob University of Maryland ECE Dept.
PMOS I-V Plot l
All polarities of all voltages and currents are reversed -2
VDS (V)
-1
0 0
VGS = -1.0V
-0.2
VGS = -1.5V
-0.4 -0.6
ID (A)
SLIDE 43
VGS = -2.0V -0.8
VGS = -2.5V
-1 X 10-4
PMOS transistor, 0.25um, Ld = 0.25um, W/L = 1.5, VDD = 2.5V, VT = -0.4V
Note y-axis scale (because W/Lp = W/Ln) (drive current: ID when VGS = VDS = VDD) UNIVERSITY OF MARYLAND
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
Review: RC Circuits
Bruce Jacob University of Maryland ECE Dept. SLIDE 44
VC = ?
R
vc(t)
V
C t
v out(t) = ( 1 – e
–t ⁄ τ
)V
τ = RC
RC time-constant: dictates how rapidly the output voltage reacts to the voltage rise on input (step function). Larger RC, slower response
UNIVERSITY OF MARYLAND
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
Capacitances VGate
VSource
Bruce Jacob University of Maryland ECE Dept.
VDrain
Gate n+
SLIDE 45
n+ Gate is capacitor
p (bulk) Depletion Regions are capacitors
C gate
WLε ox = ----------------t ox
C SC
Aε si = ---------t si
C diff
I ⋅ τc = ----------V th
Yes, there are others … Result: parasitic capacitances hinder switching speeds UNIVERSITY OF MARYLAND
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
Body Effect
Bruce Jacob
VSource > 0
University of Maryland ECE Dept.
VGate
VDrain
Gate n+
SLIDE 46
n+
p (bulk/body)
•
•
Suppose source and body are not in equilibrium: reverse bias increases size of depletion region around that diode (and changes its parasitic capacitance) Called “body effect” … it changes the threshold voltage for that device 2qε si N A ∆V t = ------------------------- ( φ S + V SB – φ S ) C ox
But can it happen? UNIVERSITY OF MARYLAND
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
Body Effect
Bruce Jacob
NAND gate
University of Maryland ECE Dept.
VDD
SLIDE 47
A
B
A
output #A
GNDeffective for #A B
•
• UNIVERSITY OF MARYLAND
#B
If #B propagates signal in non-zero time, the effective source voltage for #A can go positive (higher than ground) Perspective: Things start to get interesting when you start connecting these things together …
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
CMOS Inverter Layout I
Bruce Jacob University of Maryland ECE Dept. SLIDE 48
N-regions for source, drain
Gate (poly)
P-regions and gate for PMOS device
input
GND NMOS
output
PMOS N-Well
Cut line
UNIVERSITY OF MARYLAND
VDD
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
CMOS Inverter Layout II
Bruce Jacob
VDD
University of Maryland ECE Dept.
+
SLIDE 49
a
tub ties out transistors a
out
GND
Another view (note: wells/tubs not shown) UNIVERSITY OF MARYLAND
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
CMOS Inverter: Analysis VDD
Bruce Jacob
Rp
University of Maryland ECE Dept.
VDD
SLIDE 50
Vin = 0 CL
Rp Vout VDD
Rn
CL (load) Vin = VDD CL Rn
• UNIVERSITY OF MARYLAND
Gate response time is determined by the time to charge CL through Rp or discharge CL through Rn
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
CMOS Inverter: Transfer Plot
Bruce Jacob University of Maryland ECE Dept.
NMOS off PMOS res
2.5
NMOS sat PMOS res
2
Vout (V)
SLIDE 51
1.5
NMOS sat PMOS sat
1 NMOS res PMOS sat
0.5
NMOS res PMOS off
0 0
0.5
1
1.5
Vin (V)
UNIVERSITY OF MARYLAND
2
2.5
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
CMOS Inverter: Current
Bruce Jacob University of Maryland ECE Dept.
NMOS off PMOS res
2.5
NMOS sat PMOS res
2
Vout (V)
SLIDE 52
1.5
NMOS sat PMOS sat
1 NMOS res PMOS sat
0.5
NMOS res PMOS off
0 0
0.5
1
1.5
Vin (V)
UNIVERSITY OF MARYLAND
2
2.5
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
Properties of CMOS
Bruce Jacob University of Maryland ECE Dept. SLIDE 53
•
Full rail-to-rail swing -> high noise margins
•
Logic levels not dependent upon the relative device sizes -> transistors can be minimum size -> ratioless Always a path to Vdd or GND in steady state -> low Ω range) -> output impedance (output resistance in kΩ large fan-out (albeit with degraded performance) Extremely high input resistance (gate of MOS transistor is near perfect insulator) -> nearly zero steady-state input current
•
•
UNIVERSITY OF MARYLAND
•
No direct path steady-state between power and ground -> no static power dissipation
•
Propagation delay function of load capacitance and resistance of transistors
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
Capacitive Load, etc.
Bruce Jacob University of Maryland ECE Dept. SLIDE 54
Fan-out Fan-in
Fan-out: number of gates connected to the output of the driving date •
Gates with large fan-out are slower
Fan-in: the number of inuts to the gate •
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Gates with large fan-in are bigger and slower
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter Bruce Jacob
Aside:is capacitance all bad? Slows down output …
University of Maryland ECE Dept.
Bigger capacitor, more charge to change voltage => SLOWER
SLIDE 55
… but stabilizes power supply Bigger capacitor, more charge to change voltage => more stable power-supply voltage levels
Capacitors are de facto frequency filters … can be a good thing (“bypass caps”) UNIVERSITY OF MARYLAND
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
Transistor Sizing I
Bruce Jacob
W
University of Maryland ECE Dept. Source
SLIDE 56
L/Wmin
2W L
L Drain
(R1,C1)
(R2,C2)
The electrical characteristics of transistors determine the switching speed of a circuit •
Need to select the aspect ratios (W/L)n and (W/L)p of every FET in the circuit
Define Unit Transistor (R1, C1) • • • UNIVERSITY OF MARYLAND
L/Wmin-> highest resistance R2= R1 ÷ 2 and C2= 2 • C1 Separate nFET and pFET unit transistors
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter Bruce Jacob University of Maryland ECE Dept.
Long MOSFETs poly
Short
S
Long
S
metal active
SLIDE 57
G
G
n-well via
D
D S
Really Long D UNIVERSITY OF MARYLAND
G
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter Bruce Jacob University of Maryland ECE Dept.
Wide MOSFETs poly
Narrow
S
Wide
S
metal active
G
G
SLIDE 58
n-well via
D
G
D S
Really Wide UNIVERSITY OF MARYLAND
D
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
Transistor Sizing II
Bruce Jacob University of Maryland ECE Dept.
Resistance of MOSFET: 1 L R n = ---------------------------------------------- ----µ n C ox ( V GS – V Tn ) W
SLIDE 59
•
Increasing W decreases the resistance; allows more current to flow
Oxide capacitance C ox = ε ox ⁄ t ox [F/cm2] Gate capacitance C G = C ox WL [F] W W Transconductance β n = µ n C ox ----- = k' n ----- L L (units [A/V2]) UNIVERSITY OF MARYLAND
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
Transistor Sizing II
Bruce Jacob University of Maryland ECE Dept. SLIDE 60
nFET vs. pFET 1 R n = ------------------------------------β n ( V DD – V Tn ) 1 R p = ---------------------------------------β p ( V DD – V Tp ) µn ----- = r µp
W β n = µ n C ox ---- Ln W β p = µ p C ox ----- Lp Typically (2 .. 3)
(µ is the carrier mobility through device)
UNIVERSITY OF MARYLAND
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
Inverter Switching Point
Bruce Jacob University of Maryland ECE Dept.
Where Vin = Vout NMOS off PMOS res
2.5
SLIDE 61
NMOS sat PMOS res
Vout (V)
2 1.5
NMOS sat PMOS sat
1 NMOS res PMOS sat
0.5
NMOS res PMOS off
0 0
0.5
1
1.5
Vin (V) UNIVERSITY OF MARYLAND
2
2.5
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
Inverter Switching Point
Bruce Jacob University of Maryland ECE Dept. SLIDE 62
At all points IDSn = IDSp (drain currents) At switching point, Vin = Vout = Vsp βn βp 2 2 ------ ( V SP – V Tn ) = ------ ( V DD – V SP – V Tp ) 2 2 βn ------ ⋅ V Tn + ( V DD – V Tp ) βp V SP = ------------------------------------------------------------βn 1 + -----βp For Vsp = Vdd/2, assuming VTn= VTp, ßn = ßp => Wp ≈ 2–3Wn (equal drive currents, equal Reff: Rn = Rp)
UNIVERSITY OF MARYLAND
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
The Result (Wp = 2Wn, .25µm)
Bruce Jacob University of Maryland ECE Dept.
In metal1-poly via
metal1
polysilicon
SLIDE 63
metal2
VDD
pdiff PMOS (4/.24 = 16/1) NMOS (2/.24 = 8/1) metal1-diff via ndiff GND metal2-metal1 via
UNIVERSITY OF MARYLAND
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
The Result II (Wp = 3Wn)
Bruce Jacob University of Maryland ECE Dept.
VDD
PMOS 1.125/0.25
SLIDE 64
1.2µm λ =2λ In
Out Metal1
Polysilicon
NMOS 0.375/0.25
GND
PMOS devices 3x larger than NMOS devices UNIVERSITY OF MARYLAND
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
Delay Definitions
Bruce Jacob
Vin University of Maryland ECE Dept.
Vout
Vin
Propagation Delay tp = (tpHL + tpLH) / 2
SLIDE 65
50%
Input Waveform
Vout
time
tpLH
tpHL
90%
50% Signal slopes Output Waveform UNIVERSITY OF MARYLAND
10% tf
tr
time
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
Inverter Switching Delay
Bruce Jacob VDD
University of Maryland ECE Dept. SLIDE 66
VDD
Rp CL
VOUT
VOUT
CL
CL
Rn Charging: Vout rising
Discharging: Vout falling
If (W/L)p = r(W/L)n then ßn = ßp (and Rn = Rp) … symmetric inverter Make pFET bigger (wider) by factor of r
UNIVERSITY OF MARYLAND
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
Inverter Switching Delay
Bruce Jacob VDD
University of Maryland ECE Dept. SLIDE 67
VDD
Rp CL
VOUT
VOUT
CL
CL
Rn Charging: Vout rising
Discharging: Vout falling
tpLH = ln(2) Rp CL = 0.69 Rp CL tpHL = ln(2) Rn CL = 0.69 Rn CL tp = (tpHL + tpLH)/2 = 0.69 CL(Rn + Rp)/2 (note: the ln(2)RC term comes from first-order analysis of simple RC circuit’s respose to step input ... time for output to reach 50% value)
UNIVERSITY OF MARYLAND
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
Inverter Pair
Bruce Jacob University of Maryland ECE Dept.
VDD
PMOS 1.125/0.25
SLIDE 68
1.2µm λ =2λ In
Out Metal1
Polysilicon
NMOS 0.375/0.25
UNIVERSITY OF MARYLAND
GND
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
Inverter Pair
Bruce Jacob
Vout
University of Maryland ECE Dept. SLIDE 69
Vout 2.5V Vh Vth
Vtl Vl Output Waveform
UNIVERSITY OF MARYLAND
ENEE 359a Lecture/s 3-5 Transistors & CMOS Inverter
Dynamic Power Dissipation
Bruce Jacob University of Maryland ECE Dept.
VDD
VDD
Rp
Ctot
SLIDE 70
VOUT
VOUT
CL
CL
Rn
T
Charging: Vout rising
I avg
Q Ctot V DD ⋅ C tot = ------------ = -----------------------T T 2
P avg = V DD ⋅ I avg UNIVERSITY OF MARYLAND
Discharging: Vout falling
C tot ⋅ V DD 2 = ------------------------ = C tot ⋅ V DD ⋅ f CLK T